Pulse-code modulator



May 8, 1956 F. DE JAGER PULSEI-CODE MODULATOR 2 SheetsSheet 1 Filed March 20, 1951 NETWORK Pl/L5E (ODE DEMOI/L/ITOR CARRIE'R MODULATOR K 5 ULSE am:

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INVENTOR FRANK 0 JAG BY W% AGENT May 8, 1956 DE JAGER 2745063 PULSE-CODEI MODULATOR Fil8d M8.IGh 20 l95l 2 Sheets-Sheet 2 INVENTOR FRANK DE%LAGE Y M AGEN nited States Patent O PULSE-CODE MODULATOR Frank de Iager, Eindhoven, Netherlands, assignor to Hartford National Bank and Trust Company, Hartford, Conn., as trustee Applicatiou March 20, 1951, Serial N0. 216,486

Claims priority, apflication Netherlauds March 29, 1950 9 Claims. (C1. 332-11) This invention relates to pulse-code modulators and may be used with particular advan=tage for the direct transrnission of pulsecode modulated voice, music or television signals, which within established limits, vary both in amplitude and in frequency, as distinguished from Morse code and similar signals which do not vary at random in amplitude and frequency, alt-hough Morse signals can also be transmitt=ed with the use of the invention.

Pulse-code modulation is characterized by the combined use of time and amplitu-de quantization.

The use of time quantization is to be Kalten to mean thatonly such pulses are taken from the pulse code modulator as coincide wibh ulses contained in a series of ulses each pulse of Which is separated from the adja- -cent pulse by the same Inne interval; such pulses are termed equidistant pulses. An arrangernent of this type substantially eliminates transrnission errors introdu-ced int-o the receiver due to time shifts of the signal ulses caused by the use of pulse regenerators. Particularly when transmitting signals through a plurality of relay transmitters, 'this constitutes a special advantage which is absent from pulse position modu-lation and other kinds of pulse modula'tion. Wiuh time-multiplex transmission of a'plurality of signals, ti-me quantization a-t the same time may be utilized to minirnize cross-talk between diflerent ehannels.

Whereas in other conventional modulation methods any instantaneous value cf the signal within certain limits can be transmitted, the use of amplitud=e quantization only permit1s the transmission of a limited nurnber of amplitude levels. Thus, for exaample, it is possible to transrnit pulse-code modulated voice signals makinguse of a binary fiv.e-digit code. In this system only 32 difierent amplitude levels ean be transmitted. The signal to be transmitted 1's sampled at equally spaced timeinterval-s, |but instead of transrnitting the instantaneousvalues of the signal which occur at these time intervals, the hearest of the 32 transrn-issible amplitude levels i s transmi-tted, since the transrnitted level is ooded in a code-pulse group modulator. When using a five-digit code, this group is composed of not m01'e than live e'quzil and equidistant pu-lses. The presence or the absence of one 01' more digit-pulses of a code-pulse group characterizes this amplitude level and thus approxirnates the instantaneous amplitud'e of the signal. The pulse groupstransmitted are equidistant and exhibit a recurrence frequency (cycle frequency) which is approxirnately twice the maxirnurn signal frequency to be transmitted. f

Furthermore, pulse-oode modulators have been suggested in which the signals to be transmitted control a pulse modulator connected to a ge'nerator of equidistant ulses, the system also containing a return cireuit shunting the pulse modulator comprising a pulse-code demodulator, which is oonnected in series With a signal frequency integrating network and a device terrned a ditference producer. This device also receives the signal to be transmitted. Thus the difference producer rece ives both the signal from the return circnit and the signal to be trans- Patented May s, 1956 mibted and develops in its output circuit a difierence vo1tage whose polarity may be positive or negative depending upon whether the instantaneou-s value of the return voltage is greater or smaller than the instan-taneous va1ue of the signal to be transmit-ted. Viewed in a time diagram this return voltage Winds about the incoming signal. Under the control of the polarity of this diffierence voltage, the pulses frorn the pulse genera-tor are either suppressed or supplied by the pulse modulator to the output oircuit of the pulse code modulator.

In the present pul-se-eode modulators containing a. return circuit, the amplitude of the return voltage may exceed the amplitude of the signal voltaage a'pproximated by it, in contradistinction to the feedb.ack known for linear arnplifiers.

The term signal frequencies integrating network is to be undenstood to mean a network which supplies an ou'tput voltage which is proportional to a time integral of the input voltage over the complete frequency range of the signals to -be transmitted or over a material portion of this range. Consequently, the reciprocal value of the transmission factor (ratio between output and imput vollkages) of the nework is, for exa rnple proportional to the frequency of the voltage supplied thereto within this signal-frequency -range. In a simple form, such a network consists of =a series resistance and a -transverse oa'pacitor of such value that 21r times the 'time consbant is approximately equal to one cycle of a lower or of the lowest signal frequency. Consequently, in the case of a constant A. C.input voltage, the -output voltage decreases with an increase in signal frequency; in contradistinction to a 10W- pass filter which al-lows all signal frequencies I0 pass substantially equally.

Whereas in the first mentioned transmitter-s for pulsecode modulation With the use of a special pulse group code the outpi1t pulses represent the .approximate signal amplitude at any given moment, the pul:se Code modulators With return circuit produce ou-tput pulses which represen-t, at any instant of transmission, substantially only the difierence of the then occurring instantane-ous amplitude of the signal Will-h respect to the instantaneous amplitude of the signal at the preceding instant of transmission. This difference is substantially independent of the amplitude of the signal over at least a material portion of the frequency ran'ge to be transmitted.

These plse-code modulators comprising a return circuit may be so constructed that only the polarity of the dilference voltage is characterized (one-unit code) or (=as in U. S. patent applicatitm Sex. N0. 75,663 filed February 10, 1949, now Patent N0. 2'662113) the quantized instantaneous Value of the diiference voltage(muLti-units code) is reproduced by a bi nary pulse-group or similar cocle.

Since a limited number of amplitude levels is used in pulse-code modulation, only an approximation of the signal is transmitted. This produces a certain quantization noise, which is directly connected withthe value of an amplitude quanturn. By reducing the amplitude quanta the quantization noise may be reduced, laut this involves rapidly increasing technical difficulties with respect to the oodirrg and decoding .appara'tus; in addition the higher pulse recurrence frequenciesthen required rnay be very objeetionable.

lt has been suggested to obviate these disadvantages by usirig, at the transmitter end, a frequency-independent, exponentially -varyiug amplitudia-com;iression cf the signals to be transmitted. Thus, only signals of lowfamplitude are substantially unaltered, so that corresp onding amplitude expansion is required at the receiver side. Thereby, the qantization noise is no t really reduded, but its dist1irbing effect is dirhinished in the case of low signal voltages, so that the quantization noise apparently decreases.

The object of the invention is to improve pulse-code modulators comprising a ret'urn circuit such that with the same value of the amplitude quanta a more accurate reproduction of the signals is possible, and, in the range of the signal frequencies, a virtually reduccd quantization noise is ensured.

According to the invention, in pulse-code modulators comprising a return circuit of the said type and the series combination of a signal frequencies integrating nctworl; and a diflerence producer controlled by the return voltage and the signals to be transmitted, the series cornbination comprises an additional network which integrates the pulse frequencies located between signal frequencies and the recurrence frequency of the equidistant pulscs.

In the present specification, the term network which integrates the pulse frequencies located between signal frequencics and the recurrence frequcncy of the equidistant pulses, briefly termed pulse frequencies integrating network. is to be undersfood to rnean a network which prcduces an output voltage proportional to a time integral or a multiple time integral, of the input voltagc within the saicl range of the pulse frequencies occurring in the return voltage and which otherwisc allows all signal frequencies to pass with susbtantially equal amplitucle and allows thcse signal frequencies 10 be transmitted with a high degree of fidelity.

The two integrafing networks are preferably so comstructed that the reciprocal value of the transmission factor cf the said. series-connection is approximately proportional t frequencies lying within the signal frequency range, and is proportional to at least the square of the frequency in the frequency range between the maximum signal frequency and substantially one half the maximum pulse rccurrence frequency, and again is approximately proportional to the frequency in regard to higher frequencies.

By the invention the spectral division of the quantization noi'se energy is greatly changed; since this noise energy is reduced in the signal frequency band. The noise energy is increased for frequencies exceeding the signal frequency band, but this is not troublesorne in Signal reproduction at the receiver side, since these frequencies exceeding the signal frequency band are suppressed.

lt should be noted here that with the use of two signalfrequencies integrating networks in the return circuit the circuit-arrangernent tends to become unstable.

The improvement of this invention over pulse-code modulators without pulse-frequencies integrating network appears from the following.

With the use of a pulse-frequencies integrating network the circuit-arrangement tends to transmit the pulses, in contradistinction to former circuit-arrangements, in such manner that, viewed in a period of time comprising few periods of the highest pulse frequency occurring in the return voltage, the time integral of the divergcnces of the return voltage with respect to the signal voltage in positive and negative direction becornes approxirnately zero. This also involves that variations of an input direct voltage, which did not produce a variation of the pulse train emittcd in the former pulse-ende modulator, now produce a corresponding variation of the pulse train cmitted, although with a slight delay which is immaterial to the frequencies to be transmitted themselves.

Thus, the response level of the pulse code-modulator has been changed advantageously which is equivalent to a reduction of the amplitude quanta.

It has been found to be particularly advantageous to include a resonance circuit in the series-connection of the return circuit, this resonance circuit being preferably tuned so that, when a pulse is supplied to this series-connection, the output voltage of the series-connection comfains an alternating switching-in voltagc, the frequency of which corresponds with a higher sigma] frequency.

In order that the invention may be more clearly understood and readily carried into effect, it will now be described more fully with reference to the accompanying drawings, given by way of examplc.

Fig. 1 illustrates a pulse-code modulation transmitting system which demonstratcs the basic invention.

Fig. 2 represents a modification of Fig. l.

Fig. 3 shows damping curves to explain the proportioning of the series connection of integrating networks used in accordance with the invention.

Fig. 4 shows a particularly advantageous form of the series-connection of two integrat'ing networks used in accordance with the invention.

Fig. 5 shows, by way of explanation thereof, diagrams cf input and output voltages ot' the series-connection shown in Fig. 4.

Fig. 6 represents a time diagram 0f signal and return voltages in a typical known pulsc-code modulation.

Fig. 7 represents a time diagram of signal and return voltagcs in a pulse-code modulator according to the invention.

Finally, Fig. 8 shows the series-connection of a numbcr of integrating networks as may also be uscd in accordance with the invention.

The transrniter shown in Fig. 1 comprises a pluse generator 1 producing equidistant digit pulses which i1re supplied to a pulse modulator 2. The pulse modulator 2 is shown diagramatically as a change over switch. In accordance with the polarity of the voltage supplied to the pulse modulator through a line 3, the pulses from pulse generator 1 are supplied to line 4 or 5. The pulses appearing in the line 5 modulate a carrier-wave from a carrier-wave oscillator 6 in a modulator 7, to the output circuit of which a transmitting antenna 8 is connected. The supply line 5 to the carrier modulator 7 may include so-called regenerators to improve the form or to modify the durafion of the pulses to be ernitted.

The pulse modulator 2 is shunted by a return circuit which comprises the series connection successively of a pulse-code demodulator 9 fed by the modulator 2, a signalfrequencies integrating network 10 included in the output circuit thereof, a pulseirequencies integrating network 11 and a ditference producer 12. In addition to the return voltage across the linc 13, the Signal to be transmitted is also supplied to the difference producer by way of linc 14.

The circuit-diagrarn shown in Fig. l does not show in detail the pulse generator l, the pulse-code modulator 2, the pulse-code demodulator 9 and the difference. producer 12, since this 1's immaterial to a good undcrstanding of the present invention. For various otential detailed embodiments of these elements reference is made to the detailed views in the copcnding U. S. patent application Ser. N0. 75,663, now Patent N0. 2.662.113.

As stated above, the return circuit shunting the pulsecode modulator 2 cornprises the series connection of two integrating networks; the first integrating network 10 is a signal frequcncies integrating networl; and comprises a series resistance 15 and a parallel capacitor 16. The second integrating network 11 connected to the output terminals of the signal-frequencies integrating network 10 is a pulse-frequencies integrating network and comprises a series resistance 17, the parallel irnpcdance consisting of the series-connection of a capacitor 18 and a coupling resistance 19. The coupling resistance 19 has the eflect that part of the output volmge of the first signal-frequencies integrating network occurs between the output terminals of the pulse-frequencies integrating network 11, together with the integration voltage across the capacitor 18.

The sequence in the series-connection of the integrating networks 10, 11 and the difference producer 12 illustrated in Fig. 1 may be modified.

Fig. 2 shows a transmitter circuit-diagram substantially corresponding to that shown in Fig. l, elements corresponding to thoseof Fig. 1 bearing the Same reference numrals. In Fig. 2, however, the pulse freqnencies inte'grating network 11 and the difference producer 12 have ch1nged places Owing to this change the pulse freqnencies ifitegrating network 11 is now located between the diflerence prodncer 12 and the pi1lse-code modulator 2, so that the signal to be transmitted which is supplied to the diiference producer 12 through the line 14, is led through the pulse frequencies integrating network 11. In order to correct for any amplitude distortion due there to, the input line 14 niay include a compensation network 20. For the sake of s plicity the interchangeability 01 the dements 10, 11 and shown in Figs. 1 and 2 is no longer observed hereinafter;

essential is the use of two integrating netW0rks, one cf which op erates in an integrating manner forfhe frequency band of the speech or music signals to be transrnitted and for pulse frequencies, and the other integrating only with regard to pulse frequencies exceeding the Signal frequemy band. For frequencies of the frequency band of the speech or music signals to be transmitted, which band extendsfor exarnple from 0.3 kc. to 3.4 kc., essentially single integration occurs, double integration occurring Within a freQuency band exceeding the former.

Fig.3 shows the attenuation curves of thenetworks used, the frequency being plotted in a logarithmical scale on the horizontal axis, the attenuation in dbon the vertical axis. Curve A shows the attenuation produced by the si'gnal frequencies integrating network. This network isproportioned so that for frequencies exceeding 0.3 kc. thereciprocal value of the transmission factor increases lirliearly'with the frequency (slope approxirnately 6 db per octave). The pulse frequencies integrating network behav6s for frequencies between 0.3 kc. and 3.4 kc. as a low-pass filter, but the time constant is such that for frequencies exceeding 3.4 kc. an integrating eflect is ensllred, owing to which the said reciprocalvalue for this netWork increases linearly With the frequency. Owing to the series-connection of the two integrating fietworks the said reciprocal value for the series-connection in excess of 3.4 kc. increases quadratically with the frequency (slope apProximately 12 db per octave).

If the recur rence frequency of the pulses supplied by the pulse modulator 1 1's 60 kc., in view of the quantization nise, it is desirable to provide that forthis maximurn pulse recurrence frequency no double integration should ocour inthe return circuit. T0 this end the pulse frequencies integrating network 11 cornprises a coupling resistance 19; the value of which is chosen in connection with the v*alueof the capacitor 18 such that the time coustant of these elements together is approximately equal 12 of the circuit-arrangements tohalf the time interval between two successive ulses.

Thus', for frequencies exceeding 30 kc. the effect of the pulse frequencies integrating network 11 011 the phase shift of the return voltage across the line 13 is substantially negligible. The attenuation of the series-connection of the integrating networks 10 and 11 then varies in accordankze with curve B in Fig. 3. For frequencies lower than 0.3 kc.,1he series-connection behaves essentially as a loW-pass filter: between 0.3 and 3.4 kc. single integrationoccuts and the reciprocal value of the transmission factor inc'reaSes linearly Witl1 the frequency; between 3.4 and 30 kc. double integration occurs and the said recipro- Cal value increases quadratically with the frequency; for higher frequencies again single integration occurs and the ti0n of a coil 21, a dainbing resistance 22 and a capezoitof 23. If a pulse voltage V1 is supplied to the input of the series-connection, as shown in the time diagrarn of Fig. 5,1he output voltage of the series-connection would exhibit the variationdesignated Vu in Fig. 5 in the absence of the resonant circuit. Owing to the presence of the resonance circuit, however, the output voltage of the series-connection varies as shown at Vu'. Owing to building up phenomena the output voltage Vu, has a damped alter'nating voltage c0mponent, the frequency of Which corresponds With a higher signal frequency of, say 2.7 kc. T0 illustrate the latter, pulses with a recurrence frequency of 60 kc., as supplied by the pulse generator 1 in Figs. 1 and 2, are plotted on the time axis in Fig. 5.

Suitable values of the elements of the circuitarrangement shown in Fig. 4 With a maximum pulse recurrence frequency of 60 kc. and a signal frequency band of approximately 0.3 to 3.4 kc. have been found to bez pacitors 16, 18 and 23 are practically considered to be parallel connected and singleiintegration occurs.

In the frequency range 'of approximately 1 kc. to 3 kc., in the absence of coil 21, the attenuation already would increase as in the Gase of double integration. Owing to the presence of this coil, however, the impedance of the circuit connected in parallel With the capacitor 18 becomes gra'1dually higher with an increase in frequency. The output voltage of the network is thus higher than in the absence of the coil, since at 10W frequencies the capacitors 18 and 23 may be considered to be connected in parallel, 'wher'eas at high frequencies only the capacity of the capacitor 18 is essential. Consequentlysingle integration occurs also in the range from approxirnately 1 kc. to 3 kc. In the frequency range of approximately 4 kc. to 30 kc., double integration occurs, and for frequencies exceeding 30 kc. the effect of the capacitors 18 and 23 is negligible, so that the resistances 17 and 19 constitute a grounded potentiometer, only the resistance 15 and the capacitor 16 being of primary importance and the network having a sirigle integrating effect.

The efiect of the use of the pulse frequei1cies integrating network in the return circuit will now be set out with reference-to Figs. 6 and 7.

As stated in the preamble, in circuit-arrangements of the present kind, the return circuit has produced across it at the input cf the difference producer a voltage which Winds about the input voltage. In Fig. 6, Es designates the signal voltage supplied to the diiference producer and Er the rectangular return voltage across the return circuit.

In former pulse-code modulation arrangements with the use of Single integration in the return circuit, a signal voltage of the value indicated in Fig. 6 is too 10W to produce a variation of the return voltage and consequenfly of the pulse train emitted. With the use of an additional pulse-frequencies integrating network comnected in series with a Signal frequencies integrating net work; matters are different as shown in Fig. 7. The pulse frequencies integrating network provides, in eifect, that after a few periods of the maxirnurn pulse recurrence frequency (60 kc.) a variation of the pulse'train emitted and consequently of the return voltage occurs in a manner such that in a tirne comprising several periods of the maximum pulse recurrence frequency the integral value of positive differences between the return voltage Er and the signal voltage Es becomes approximately equal to the integral value of negative ditferences between the voltages Es and Er. Figs 6 and 7 give an impression of the said integral values by comparison of the extents of the differently cross-hatehed surface areas. If use is made of the invention the circuit-arrangement tends to equal integral values, in contradistinction to former circuit-arrangements which operate in the manner shown in Fig. 6. This mcans an improved response level of the pulse-cocle modulator and is equivalent to a reduction of the arnplitude quanta used. This reduction of the quanta, however, is ensured without the use of a higher pulse reeurrcnce frequency.

Instead of efieeting double integration, as in Figs. 1, 2 and 4, for pulse rccurrence frequencies exceeding the signal frequency band, more than double integration may take place, the reciprocal value of the transrnission factor of the series eonnection in the return circuit increasing by the third or cven a still higher power of the frequency, for exarnple in a range between 4 and 30 kc. In this case, partieuiar attention should be focussed to sufficient stability of the circuit-arrangernent, for which purpose the phase shift of this network in the range of the signal frequeneies must remain below 180. In order to achieve this, it is (.dVantgclls to combine the output voltages of the serL..connected integrating networks in a suitable mixing ratio. for which purpose use may be made of a series-conneeiion as shown in Fig. 8. This series-connecli0n comprises four integrating networks 24, 25, 26, 27, corresponding output terminals being connected through separate resistors 23, 29, 30 and 31 to a cornrnon output resistor 32 of the series-cormection.

What l claim is:

l. Apparatus for translating intelligence signals having a predetermined frequency range into code modulated pulses having a repetition rate substantially higher than the maximum frequency in said frequency range, said apparatus comprising a pulse code modulator yielding code modulated pulses, means to supply to said modulator pulses of said repetition rate, a return circuit for said modulator and inelncling a pulse code demodulator, a first network integrating all voltages whose frequencies fall within said signal frequency range, a seeond network integrating all voltages whose frequencie fall between the maximum frequency of said signal frequency range and said repetition rate and a difierence producer having first and second input circuits, said producer having amplifying churacteristics ut which the voltage produced in the output tl.creof is proportional to the difference in the voltngcs supplis-d 10 said input circuits, the output of said pulse code modula=tor being fed scrially through said dcmodulator. said net=v0rl s und through the first input circuit o? said dificrence producer circuit to the input of the pulse code modulator, and means to supply the intelligence Signal through the second input circuit of said ditference producer to the input of said modulator.

2. Apparatus for translating intclligence signals having a predetermined frequeney range into code modulated pulses having a repetition rate substantially higher than the maximum lrequensy in said frequeney range, said apparatus comprising a pulse code modulator yielding code mout. ateo' pulses, means to supply to said modulator pulses of said repctition rate, a return circuit for said modulcttor und including a pulse code demodulator, a first reiwork integruting all voltages whose frequencies fall witlxin said signal frcquency range, a second network intcgrating all voltages whose frequencies fall between the muximum frcquency of said signal frequency range and said repetition rate and a difference producer having first and second input circuits, said producer having amplifying charaeteristics at which the voltage produced in the output thereof is proportional to the diiference in the voltages supplied to said input circuits, the output of said pulse code modulator being fed serially through said demodulator, said first and second networks and the first input circuit of said ditference producer circuit in the order narned to the input of the pulse code modulator, and means to supply the intelligence signal through the second input circuit of said ditference producer to the input of said modulator.

3. Apparatus, as set forth in claim 2, wherein the second network includes a resonant circuit 4. Apparatus, as set forth in claim 3, wherein the resonant circuit is tuned to a frequency at which the entput voltage of the second network will include a transient alternating voltage having a frequency which substantially corresponds to the central frequeney in said rangc.

5. Apparatus for translating intelligence signals having a predetermined frequency range into code modulated pulses having a repetition rate substantially higher than the maxirnum frequency in said frequency range, said apparatus comprising a pulse code modulator yielding code modulated pulses, means to supply to said modulator pulses of said repetition rate, a return circuit for said modulator and including a pulse code demodulator a first network integrating all voltages whose frequencies fall within said signal frequency range, a second network integrating all voltages whose frequencies fall between the maximum frequency of said signal frequency range and said repetition rate and a difference producer having first and second input circuits, said producer having amplifying characteristics at which the voltage produced in the output thereof is proportional to the ditference in the voltages supplied to said input circuits the output of said pulse code modulator being fed serially through said demodulator, the first network, the first input circuit of said difierence producer circuit, and said second network in the Order named to the input of the pulse code modulator, and means to supply the intelligence signal through the second input circuit of said difference producer to the input of said modulator.

6. Apparatus, as set forth in claim 5, wherein the second network ineludes a series resistance and in parallel with said resistance a series cornbination of capacitance and resistance.

7. Apparatus, as set forth in claim 5, wherein the series combination oi capacitance and resistance has a time constant substantially equal to half the time interval between successive code modulated pulses.

8. Apparatus, as set forth in claim 5, wherein a series resonant circuit is connected in parallel with the capacitance of said second network.

9. Apparatus for translating intelligenee Signals having a predetermined frequency range into code modulated pulses having, a repetition rate substantially higher than the maximum frequency in said frequency rangc, said apparatus comprising a pulse code modulator yielding code modulated pulses, means to supply to said modulator pulses of said repetition rate, a return circuit for said modulator and including a pulse code demodnlator, a first network integrating all voltages wl1ose frequencies fall within said signal frequeney range, a second network integrating all voltages whose frequencies fall betwecn the maximurn frequency of said signal frequency range and said repetition rate, said second network including a pluralily of elementary networks the outputs of which are supplied through separate resistors to a common output resistor of said second network, and a ditference producer having first and second input circuits and having amplifying characteristics at which the voltage produced in the output thcreof is proportional to the dilference in the voltages supplied to said input circuits, the output of said pulse code modulator being fed serially through said demodulator said networks and through the first input circuit of said difference producer circuit to the input of the pulse code demodulator, means to supply the intelligence signal through the second input circuit of said difference producer to the input of said modulator.

References Cited in the file of this ptent UNITED STATES PATENTS Redford Inne 29, 1937 10 Rose Sept. 12, 1939 Thomas May 3, 1949 Gloess Dec. 20, 1949 Clavier Aug. 29, 1950 Heising Jan. 30, 1951 

